# Iterative Frequency-Domain Channel Estimation and Equalization for Ultra-Wideband Systems with Short Cyclic Prefix

- Salim Bahçeci
^{1}and - Mutlu Koca
^{1}Email author

**2010**:819591

https://doi.org/10.1155/2010/819591

© S. Bahçeci and M. Koca. 2010

**Received: **4 October 2009

**Accepted: **9 June 2010

**Published: **30 June 2010

## Abstract

In impulse radio ultra-wideband (IR-UWB) systems where the channel lengths are on the order of a few hundred taps, conventional use of frequency-domain (FD) processing for channel estimation and equalization may not be feasible because the need to add a cyclic prefix (CP) to each block causes a significant reduction in the spectral efficiency. On the other hand, using no or short CP causes the interblock interference (IBI) and thus degradation in the receiver performance. Therefore, in order to utilize FD receiver processing UWB systems without a significant loss in the spectral efficiency and the performance, IBI cancellation mechanisms are needed in both the channel estimation and equalization operations. For this reason, in this paper, we consider the joint FD channel estimation and equalization for IR-UWB systems with short cyclic prefix (CP) and propose a novel iterative receiver employing soft IBI estimation and cancellation within both its FD channel estimator and FD equalizer components. We show by simulation results that the proposed FD receiver attains performances close to that of the full CP case in both line-of-sight (LOS) and non-line-of-sight (NLOS) UWB channels after only a few iterations.

## Keywords

## 1. Introduction

Recently, frequency-domain (FD) processing for receiver design has gained considerable interest, particularly in single-carrier (SC) communication systems because of the significant complexity reductions it offers while attaining the same as and often better performances than those of the time-domain (TD) methods [1, 2]. Ordinarily, to be able to employ FD processing at the receiver, a cyclic prefix (CP) that is at least as long as the channel is added to each transmitted data block such that the linear convolution of the channel and the transmitted data block can be expressed as an equivalent circular convolution operation and an FD signal model can be derived. In the FD signal model, the channel distortion appears as a single tap fading coefficient and the FD channel estimation and equalization algorithms can be implemented with simple arithmetic operations in contrast to the complex matrix inversions required by their time-domain counterparts [3].

Because of these memory/computational complexity reductions, FD processing has also emerged as powerful design tool for impulse radio ultra-wideband communication (IR- UWB) systems, which are characterized by long delay spreads [4]. For instance, minimum mean-squared error (MMSE) frequency-domain equalization (FDE) is proposed for IR-UWB and direct sequence- (DS-) UWB transmissions and their performances are compared in [5]. An SC IR-UWB system employing FD equalization (FDE) is proposed in [6], as an alternative to the multiband OFDM UWB appoaches. The proposed method achieves lower peak-to-average power ratios than that of the MB-OFDM UWB systems and is more effective in collecting multipath energy and combatting the intersymbol interference (ISI). In [7, 8], zero-forcing and MMSE FD detectors are proposed for IR-UWB systems and compared with the classical RAKE receiver. An iterative FDE for IR-UWB systems is proposed in [9] based on energy spreading transform. Finally, an FD turbo equalization and multiuser detection scheme is presented in [10] for the DS-UWB systems. Notice that these works present the FDE methods for UWB with the underlying assumption that channel impulse response (CIR) for the multipath UWB channel is available whereas the joint FD UWB channel estimation and equalization problem is addressed in [11] for SC-FDE UWB and in [12] for DS-UWB systems.

In all the works mentioned above, full CP (that is at least as long as the channel) is assumed to be inserted between transmitted blocks. However, for UWB channels where the delay spread is very large, adding full CP means a significant degradation in the spectral efficiency and throughput. On the other hand, using short or no CP for spectral efficiency causes a mismatch between the linear and circular convolution operations and thus the inter-block-interference (IBI) between the transmitted blocks. Therefore the IBI reconstruction and cancellation must be incorporated in the FD receiver design so that low complexity FD algorithms can be used without the need for full CP, which has been addressed in the related context, that is, for SC communications in [13–17] and for UWB communications in [18–20]. In [13], a reduced-CP SC-FDE system is proposed where the CP length is reduced using specifically designed frame structures. Iterative reconstruction of the missing CP is proposed and its performance on the FDE is evaluated in [14] again for SC communications. In [15], FD channel estimation problem is addressed in the presence of insufficient CP and an interference cancellation and channel estimation algorithm is proposed for SC block transmission and this method is applied to turbo equalization in [16]. Similarly, a joint iterative FD channel estimation and equalization scheme is presented for SC-FDE without CP in [17]. Regarding the UWB literatures, a CP reconstruction and FDE algorithm for IR-UWB communication is proposed with known channel coefficients in [18] based on the CP reconstruction method presented in [21] and the impact of imperfect channel estimation is presented in [19]. A different approach is also proposed in [20], where a time-division multiple access scheme is incorporated with the SC-FDE over UWB channels so as to cancel the multiple access interference and IBI effects that is due to insufficient CP, again assuming the channel knowledge is available.

To place the related works in the literature into perspective, please notice that in order for frequency-domain processing to be feasible for UWB communications, the receiver design problem needs to be addressed in a uniform framework encompassing the following criteria: ( ) frequency-domain processing for joint channel estimation and equalization for low complexity, ( ) reduced or no CP to avoid significant loss in spectral efficiency, and ( ) IBI suppression to retrieve the performance loss due to the lack of full CP (possibly via iterative processing). Unfortunately, most of the works mentioned above address one or more of these design issues, but not all of them. For this reason, we present in this paper a novel FD iterative UWB receiver architecture that preserves the spectral efficiency of UWB systems while recovering possible performance losses due to IBI with very low complexity. The low complexity is partially also due to the fact that even though the receiver is iterative, the performance gains are attained after only a few iterations.

The proposed iterative receiver consists of three soft-input soft-output (SISO) blocks: a channel estimator implemented by the FD recursive least squares (RLSs) algorithm, a minimum mean squared error (MMSE) FDE, and a repetition decoder to extract soft bit values from the pulse repetitions. The channel estimator makes an estimate of the IBI using subsequent pilot blocks in each recursion that is removed from the received signal model before a recursion of the channel estimation update is made. At the end of the pilot mode, the channel estimate is passed onto the back-end iterative receiver that is comprised of the SISO MMSE equalizer and the repetition decoder. The SISO MMSE equalizer performs soft cancellation of both IBI and ISI at its input and soft log-likelihood mapping at its output. The joint equalization and decoding iterations are carried out so as to improve the soft decisions on transmitted bits. Notice that contrary to the conventional approach, the SISO repetition decoder within the iterative receiver is not a module to decode an outer code but instead an inherent part of the UWB symbol detection architecture. The proposed iterative receiver is simulated for both line-of-sight (LOS) and nonline-of-sight (NLOS) UWB channels and simulation results indicate that even with very short CP lengths, it achieves performances that are very close to those of the full CP cases by using relatively small number of pilot blocks. Moreover, simulations also indicate that the proposed receiver performs significantly well even when there is no CP used at the transmitter side.

The rest of this paper is organized as follows: The FD signal model is presented in Section 2. Then the proposed iterative receiver structure with the IBI estimation and cancellation is presented in Section 3. Section 4 is devoted to the simulation results, and the paper is ends in Section 5 with some conclusive remarks.

## 2. Signal Model

*n*th input information sequence having bits is represented as where . Each bit is spread to by repeating every bit times where . Thus can be expressed as

where , and is the modulo operation with respect to .

*i*th path, respectively. The path delays can be approximated as integer multiples of for simplicity and the CIR can be written as

*n*th block can be expressed as

## 3. Iterative FD Channel Estimation and Equalization with IBI Cancellation

### 3.1. FD Channel Estimation

Notice that the IBI term in (19) differs from the one in (8) in employing the channel estimates instead of the real values.

Then, subsequent recursions of the FD-RLS algorithm are carried out by replacing in (15) by of (21) and cancelling the IBI estimation successively.

where and denote the soft bit values corresponding to the st and th data blocks, respectively. Notice that these soft values are computed from the log likelihood ratios (LLRs) via the hyperbolic tangent function , that is, as presented in detail in the sequel.

As for the complexity of the channel estimation algorithm, the FFT and IFFT operations for a sequence of length requires approximately real multiplications and real additions. As seen from Figure 1, in each channel estimation recursion one FFT and one IFFT is required. Another FFT operation is required for the transformation of the time-domain IBI term into frequency-domain. Notice that exact computation of the function can be costly, however it can be done via the piecewise linear approximations or coarse quantization approaches with look up table [24]. Using the piecewise linear approximation in [24] with regions, the computation of the soft symbols costs roughly about real additions and multiplication per symbol. Considering also the subtraction inside the parenthesis in (19) and the multiplication outside, the computation of the IBI term and the cancellation operations requires real products and real additions. Finally one recursion of the channel estimation algorithms employs products and additions for FD-RLS and products and additions for FD-LMS [23]. As a result, the overall computational complexity of the FD-RLS channel estimator is real multiplications and real additions per pilot block. The complexity of FD-LMS channel estimator would be slightly lower as it requires real multiplications and real additions, however its convergence is significantly slower. For this reason the FD-RLS algorithm is employed for channel estimation throughout the simulations.

### 3.2. Iterative FD Equalization and Decoding

*m*th frequency component of the estimated channel coefficient, is the

*m*th frequency component of estimated chip position, and is defined as

*n*th block is computed as

for where and are the iteration index and the total number of iterations per each received block, respectively.

Considering again the computational complexity for the back-end iterative equalizer, the IFFT and FFT operations require real multiplications and real additions in each iteration. The cost of FD MMSE equalization with IBI estimation and cancellation is real products and real additions per iteration. In simulations, convergence of the iterative receiver is observed after only two iterations, meaning that the increase in complexity due to the number of iterations is low. The complexity brought by the interleaving/deinterleaving operations and by the repetition decoder is much lower than the equalizer and channel estimator blocks, and thus it is neglected in this discussion.

## 4. Simulation Results

In this section simulation results of the proposed receiver structure are presented with different CP lengths over the UWB channel models CM1–CM4 proposed in [4] where CM1 is a line-of-sight (LOS) channel whereas CM4 is a nonline-of-sight (NLOS) channel with a long delay spread. All channel models are simulated via computer trials and run over channel realizations. Both the pulse and chip durations are chosen as 1 nanosecond, that is, In each block information bits are transmitted where each bit is spread over 4 chips. At the receiver side, matched filter outputs are sampled at the chip-rate, so each received block has 640 samples. In each channel realization, the channel impulse response changes in each run. However, for the full cyclic prefix conditions, the maximum channel spreads are assumed to be , , , and taps for the CM1–CM4 channels, respectively.

## 5. Conclusion

An iterative FD receiver is presented to combat with the deteriorating effects of using short CP for IR UB systems. An IBI estimation and cancellation scheme that can be used both with an FD channel estimator and with an FD MMSE equalizer is proposed. The FD channel estimator equipped with the IBI cancellation improves the channel estimates significantly. Employing iterative IBI cancellation within the back-end equalizer also improves the signal detection performance. We show with simulations that with moderate number of pilot blocks, the proposed receiver attains performances close to the full CP or AWGN bounds even in the case of no CP. Future works may include the analysis of the proposed system under parametric uncertainties such as the synchronization errors, channel estimation errors …, and as well as the derivation of analytical performance bounds for the channel estimation and equalization with IBI cancellation.

## Appendix

*n*th data block are caused only from th data block. Defining the term as the difference between the CIR and CP, we can write the first element of the

*n*th block that contains IBI error by convolving the CIR and transmitted data block:If the CP length were sufficient, then the first term of the

*n*th received block would beThen, the IBI error in the first element of the received vector is expressed asSimilarly, the IBI error terms for are written asAs a result, we can obtain the closed form expression of the IBI error asNotice that by definition for .

## Declarations

## Authors’ Affiliations

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