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A general solution to the continuoustime estimation problem under widely linear processing
EURASIP Journal on Advances in Signal Processing volume 2011, Article number: 119 (2011)
Abstract
A general problem of continuoustime linear meansquare estimation of a signal under widely linear processing is studied. The main characteristic of the estimator provided is the generality of its formulation which is applicable to a broad variety of situations, including finite or infinite intervals, different types of noises (additive and/or multiplicative, white or colored, noiseless observation data, etc.), capable of solving three estimation problems (smoothing, filtering or prediction), and estimating functionals of the signal of interest (derivatives, integrals, etc.). Its feasibility from a practical standpoint and a better performance with respect to the conventional estimator obtained from strictly linear processing is also illustrated.
1 Introduction
In most engineering systems, the state variables represent some physical quantity that is inherently continuous in time (groundmotion parameters, atmospheric or oceanographic flow, and turbulence, etc.). Thus, the formulation of realistic models to represent a signal processing problem is one of the major challenges facing engineers and mathematicians today. Given that in many problems the incoming information is constituted by continuoustime series, the use of a continuoustime model will be a more realistic description of the underlying phenomena we are trying to model. For example, [1] gives techniques of continuoustime linear system identification, and [2] illustrates the use of stochastic differential equations for modeling dynamical phenomena (see also the references therein). Continuoustime processing is especially suitable when data are recorded continuously, as an approximation for discretetime sampled systems when the sampling rate is high [3] and when data are sampled irregularly [4]. It is also necessary with applications that require highfrequency signal processing and/or very fast initial convergence rates. Analog realizations also result in a smaller integrated circuit, lower power dissipation, and freedom from clocking and aliasing effects [5, 6]. In such cases, the continuoustime solution becomes an adequate alternative to the discrete one since it allows realtime processing and alleviates the overload problem assuring more reliable overall operation of the system [7]. Moreover, the analytical tools developed in the continuoustime case might bring new insights to the analysis which are not possible in their discretetime counterparts. In particular, [8] illustrates this fact in the problem of sorting continuoustime signals, [9] in the problem of nonfragile H_{∞} filtering for a class of continuoustime fuzzy systems, and [10] in the study of the behavior of the continuoustime spectrogram.
The estimation problem is a topic of great interest in the statistical signal processing community. This problem has traditionally been solved by using a conventional or strictly linear (SL) processing. For instance, [11, 12] deal with classical estimation problems (e.g., the KalmanBucy filter) under a real formalism, [13] tackles similar problems in the complex field, and [14] uses factorizable kernels for solving such problems. The main characteristic of the SL treatment is that it takes into account only the autocorrelation of the complexvalued observation process, ignoring its complementary function. That is, the only information considered for the building of the estimator is that supplied by the observation process, while the information provided by its conjugate is ignored. Cambanis [15] provided the more general solution to the problem of continuoustime linear meansquare (MS) estimation of a complexvalued signal on the basis of noisy complexvalued observations under a SL processing. In fact, Cambanis's approach is valid for any type of secondorder signals and observation intervals, and it is not necessary to impose conditions such as stationarity, Gaussianity or continuity on the involved processes, nor restrictions of finite intervals.
Recently, it has been proved that the treatment of the linear MS estimation problem through widely linear (WL) processing, which takes into account both the observation process and its conjugate, leads to estimators with better performance than the SL ones in the sense that they show lower error variance. Specifically, and from a discretetime perspective, the WL regression problem was tackled in [16], the prediction problem in a complex autoregressive modeling setting was addressed in [17, 18] and later extended to autoregressive moving average prediction in [19]. Also, an augmented^{1} affine projection algorithm based on the full secondorder statistical information has been newly devised in [20]. Among the wide range of applications of WL processing is the analysis of communication systems [21], ICA models [22], quaternion domain [23], adaptive filters [24–26], etc.
The study of continuoustime estimation problems is also interesting because it provides precise information on some structural properties of the system under study [8, 9]. For instance, an explicit expression of the MS error associated with the optimal estimator can be derived in this approach (e.g., see [12, 13]). Notice that this wellknown result is independent of the number of available observations. In addition, the continuoustime solution becomes an excellent alternative to the discrete one when the number of available data is large. Discretetime solutions involve the explicit calculation of matrix inverses whose dimensions depend on the number of observations (see, e.g., [16]). In practice, the process would be cumbersome or even prohibitive if this number were large (as occurs, e.g., in a major earthquake where the workload of the system increases suddenly).
The WL estimation problem under a continuoustime formulation was initially dealt with in [27, 28] and [29]. More precisely, the particular problem of estimating a complex signal in additive complex white noise is solved in [27] or [28] through an improper version of the KarhunenLoève expansion. A general result comparing the performance of WL and SL processing is also presented in which it is shown that the performance gain, measured by MS error, can be as large as 2. Finally, [29] provides an extension of the previous problem to the case in which the additive noise is made up of the sum of a colored component plus a white one. The handicaps of both solutions are: i) they are limited to MS continuous signals, ii) the signals must be defined on finite intervals, iii) the model for the observation process involves additive noise (white noise in the case of [27] and [28]), and iv) they are only devoted to solving a smoothing problem.
In this paper, we address a more general estimation problem than those solved in [27–29]. For that, we consider the general formulation of the estimation problem given in [15], and we solve it by using WL processing. The generality of this formulation allows the solution of a wide range of problems, including general secondorder processes, infinite observation intervals, additive and/or multiplicative noise, noiseless observations, estimation of functionals of the signal, etc. It also brings under a single framework three different kinds of estimation problems: prediction, filtering, and smoothing. Hence, all the above handicaps are avoided with the proposed solution. Specifically, we present two forms of the WL estimator depending on the nature, either proper or improper, of the observation process. Then, we state conditions to express such an estimator in closed form. Closed form expressions for the estimator are convenient from a computational point of view [11, 12, 15]. Three numerical examples show that the proposed solution is feasible and demonstrate the aforementioned generality. The first one compares the performance of the WL estimator in relation to the SL one by considering an observation process defined on an infinite interval and with multiplicative noise. The second concerns the problem of estimating a signal in nonwhite noise and illustrates its application with discrete data. Lastly, the third example considers the earthquake groundmotion representation problem and illustrates a possible real application.
The rest of this paper is organized as follows. In Section 2, we review the SL solution proposed in [15]. Section 3 presents the main results. We derive the new estimator and its associated MS error. Moreover, we prove the better performance of this in relation to the SL estimator, and we give conditions to obtain a closed form of the WL estimator. The results obtained in this section are first stated and then proved rigorously in an Appendix. This section also includes a brief description of how the technique can be implemented in practice. Finally, Section 4 contains three numerical examples illustrating the application of the suggested estimator, and a performance comparison between WL and SL estimation is carried out.
Throughout this paper, all the processes involved are complex, measurable and of secondorder. Next, we introduce the basic notation. The real part of a complex number will be denoted by \mathcal{R}\left\{\cdot \right\}, the complex conjugate by (·)*, the conjugate transpose by (·) ^{H}and the orthogonality of two complexvalued random variables, say a and b, by a ⊥ b. Also, a.s. stands for almost surely and a.e. for almost everywhere.
2 Strictly Linear Estimation
A core problem in signal processing theory is the estimation of a signal from the information supplied by another signal. A very general formulation of this problem was provided by Cambanis in [15]. Specifically, let F and G be two functionals and {s(t), t ∈ S} be a random signal, where S is any interval of the real line. Suppose that s(t) is not observed directly and that we observe the process
where T is any interval of the real line. Based on the observations {x(t), t ∈ T}, the aim is to estimate a functional of s(t)
S' being any interval of the real line.
As noted above, this formulation is very general and contains as particular cases a great number of classical estimation problems, such as estimation of signals in additive and/or multiplicative noise, estimation of signals observed through random channels, random channel identification, etc. [15]. It can also be adapted to treat filtering, prediction, and smoothing problems.
In order to proceed with the building of the Cambanis estimator, the secondorder statistics of the processes involved are needed. Let r_{ x }(t, τ) and r_{ ξ }(t, τ) be the respective autocorrelation functions of x(t) and ξ(t). Let c_{ x }(t, τ) = E[x(t)x(τ)] denote the complementary autocorrelation function of x(t). Moreover, we denote the crosscorrelation functions of ξ(t) with x(t) and x*(t) by ρ_{1}(t, τ) = E[ξ(t)x*(τ)] and ρ_{2}(t, τ) = E[ξ(t)x(τ)], respectively.
The weakness of the hypotheses imposed on the processes and the possibility of considering infinite intervals force us to construct measures other than Lebesgue measure. To avoid an excess of mathematical formalism, we do not follow the Cambanis exposition literally. Changing the measure is equivalent to searching for a function F(t) such that
This function F(t) can be selected by a trialanderror method or by using the procedure given in [30], and in addition, it does not have to be unique. This freedom of choice is to be exploited appropriately in every particular case under consideration. For example, if T = [T_{ i }, T_{ f }] and x(t) is MS continuous, then we can select F(t) = 1. Some practical examples can be consulted in [31].
Condition (1) guarantees the existence of the eigenvalues and eigenfunctions, {λ_{ k }} and {ϕ_{ k }(t)}, respectively, of r_{ x }(t, τ). Next, we need an orthogonal basis of random variables built from the observation process and the Hilbert space spanned by it. The elements of such a basis take the form {\epsilon}_{k}={\int}_{T}x\left(t\right){\varphi}_{k}^{*}\left(t\right)F\left(t\right)\mathsf{\text{d}}t a.s., and let H(ε_{ k }) be the Hilbert space spanned by the random variables {ε_{ k }}. By using SL processing, the estimator {\widehat{\xi}}_{\mathsf{\text{SL}}}\left(t\right) proposed in [15] is calculated by projecting the process ξ(t) onto H(ε_{ k }). As a consequence, {\widehat{\xi}}_{\mathsf{\text{SL}}}\left(t\right) is given by
with {b}_{k}\left(t\right)=\frac{1}{{\lambda}_{k}}{\int}_{T}{\rho}_{1}\left(t,\tau \right){\varphi}_{k}\left(\tau \right)F\left(\tau \right)\mathsf{\text{d}}\tau. Moreover, its associated MS error is
3 Widely Linear Estimation
In general, complexvalued random processes are improper [24], and then the appropriate processing is the WL processing. In this section, we provide a new estimator, {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right), by using WL processing and calculate its corresponding MS error, {P}_{\mathsf{\text{WL}}}\left(t\right)=E\left[\xi \left(t\right){\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right){}^{2}\right]. To this end, we consider, together with the information supplied by the observation process, x(t), the information provided by its conjugate, x*(t). Both processes are stacked in a vector giving rise to the augmented observation process, x(t) = [x(t), x*(t)]', whose autocorrelation function is denoted by r_{ x }(t, τ) = E[x(t)x^{H}(τ)]. Notice that {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right) receives the name of WL estimator because it depends linearly not only on x(t) but also x*(t) in contrast with the conventional estimator.
In order to find an explicit form of the estimator and its error, we have to distinguish two possibilities in relation to the nature of x(t): proper or improper. If x(t) is proper, i.e., cx(t, τ) = 0, then the expression for the estimator is
where {\stackrel{\u0304}{b}}_{k}\left(t\right)=\frac{1}{{\lambda}_{k}}{\int}_{T}{\rho}_{2}\left(t,\tau \right){\varphi}_{k}^{*}\left(\tau \right)F\left(\tau \right)\mathsf{\text{d}}\tau, and with associated MS error
Expressions (2) and (3) are derived in Theorem 1 in the "Appendix". These expressions extend to the SL ones since if ρ_{2}(t, τ) = 0, then {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)={\widehat{\xi}}_{\mathsf{\text{SL}}}\left(t\right) and P_{WL}(t) = P_{SL}(t).
On the other hand, in the improper case (c_{ x }(t, τ) ≠ 0), and unlike the proper case, it is not as quick to calculate an explicit and easily implemented expression of {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right). The main difference between both cases is that now the members of the set \left\{{\epsilon}_{k}\right\}\cup \left\{{\epsilon}_{k}^{*}\right\} are not orthogonal. In fact, we have
Thus, the goal will be to calculate an orthogonal basis in the Hilbert space generated by {ε_{ k }} and \left\{{\epsilon}_{k}^{*}\right\}, H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right), which avoids this serious problem. This objective is attained in Lemma 1 in the "Appendix" by means of the eigenvalues, {α_{ k }}, and the corresponding eigenfunctions, φ_{ k }(t), of r_{ x }(t, τ). Following a similar reasoning to [28], it can be shown that the eigenfunctions φ_{ k }(t) have the particular structure given by {\mathbf{\phi}}_{k}\left(t\right)={\left[{f}_{k}\left(t\right),{f}_{k}^{*}\left(t\right)\right]}^{\prime} and are orthonormal in the sense of (10). The elements of this new set are real random variables of the form
verifying that E[w_{ n }w_{ m }] = α_{ n }δ_{ nm }. By using this new set of variables, we can obtain the WL estimator explicitly
where {\psi}_{k}\left(t\right)=\frac{1}{{\alpha}_{k}}\left({\int}_{T}{\rho}_{1}\left(t,\tau \right){f}_{k}\left(\tau \right)F\left(\tau \right)\mathsf{\text{d}}\tau +{\int}_{T}{\rho}_{2}\left(t,\tau \right){f}_{k}^{*}\left(\tau \right)F\left(\tau \right)\mathsf{\text{d}}\tau \right), and its corresponding MS error is
Theorem 2 in the "Appendix" proves these assertions.
From a practical standpoint, it would be interesting to get a closed form for {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right). For that, it is necessary to restrict the kind of processes considered so far. Theorem 3 in the "Appendix" gives conditions in order to express the estimator in the following way
for some square integrable functions h_{1}(t, ·) and h_{2}(t, ·). Expression (7) is computationally more amenable than (2) or (5). The key question is whether the conditions of Theorem 3 are fulfilled. An example of the latter is the classical problem of estimating an improper complexvalued random signal in colored noise with an additive white part addressed in [29]. Specifically, the observation process considered is
where s(t) is an improper complexvalued MS continuous random signal, the colored noise component, n_{ c }, is a complexvalued MS continuous stochastic process uncorrelated with v(t), and v(t) is a complex white noise uncorrelated with the signal s(t). Note that the formulation of the estimation problem treated in [29] is much more restrictive than that studied in the present paper.
Finally, a remarkable advantage of the proposed estimator appears when ξ(t) is a real process, and x(t) is still complex. In this case, {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right) is real too. However, there is no reason for the SL estimator to be real, which is not convenient when we estimate a real functional. Moreover, if x(t) is proper, then {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)=2\mathcal{R}\left\{{\widehat{\xi}}_{\mathsf{\text{SL}}}\left(t\right)\right\} and its associated MS error is
which provides a decrease in the error that is twice as great as the SL estimator.
Notice also that the Hilbert space approach we have followed to derive the WL estimators allows us to give an alternative proof of the wellknown fact that WL estimation outperforms SL estimation. The estimator {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right) is really obtained by projecting the functional ξ(t) onto the Hilbert space H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right). Observe that H\left({\epsilon}_{k}\right)\subseteq H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right) and then trivially by the projection theorem of the Hilbert spaces^{2} [[12], Proposition VII.C.1], we have P_{WL}(t) ≤ P_{SL}(t), for t ∈ S', and hence, the WL estimator outperforms the SL one as regards its MS error.
3.1 Practical Implementation of the Estimator
We enumerate the necessary steps in implementing the estimation technique proposed for the estimator (5). Nevertheless, some comments are made on how the algorithm can be adapted to obtain (2). Moreover, the role played by (7) becomes clear at the end of the procedure. The steps are the following:

1)
Determine the augmented statistics of the processes involved. In some practical applications, the secondorder structure is initially known. In fact, it may be derived from experimental measurements or mathematical models. For instance, the informationbearing signal in the communications problem is purposely designed to have desired statistical properties [32]. Other examples can be consulted in [33, 34].

2)
Select a function F(t) such that condition (1) holds. As noted above, this function F(t) can be selected by a trialanderror method or by using the procedure given in [30]. Notice that this function is not unique and, in general, there are many specifications possible.

3)
Obtain the eigenvalues {α_{ k }} and eigenfunctions {φ_{ k }(t)} associated with r_{ x }(t, τ). In general, determination of eigenvalues and eigenfunctions, except for a few cases, is a problem that is very involved, if not impossible. However, we can avoid the calculation of true eigenvalues and eigenfunctions by means of the RayleighRitz (RR) method, which is a procedure for numerically solving operator equations involving only elementary calculus and simple linear algebra (see [31, 35] for a detailed study about the practical application of the RR method).

4)
Truncate expressions (5) and (6) at n terms and substitute, if necessary, the true eigenvalues and eigenfunctions by the RR ones. This truncated version of the estimator, which is in fact a suboptimum estimator, can be calculated via the expression (7) with
{h}_{1}\left(t,\tau \right)=\sum _{k=1}^{n}{\psi}_{k}\left(t\right){f}_{k}^{*}\left(\tau \right)\phantom{\rule{1em}{0ex}}\mathsf{\text{and}}\phantom{\rule{1em}{0ex}}{h}_{2}\left(t,\tau \right)=\sum _{k=1}^{n}{\psi}_{k}\left(t\right){f}_{k}\left(\tau \right)
and where both functions satisfy the conditions of Theorem 3.
Thus, we have replaced the computation of 2n integrals in the truncated version of (5) (or n integrals in the finite series obtained from (2)) by the computation of two integrals in (7), and hence, it entails a reduction in the error of approximation for a given precision.
Note that both the precision and the amount of computation required in applying this method depend heavily on the number n. An easy criterion^{3} for determining an adequate level of truncation n without an unnecessary excess of computation can be the following: select n in such a way that {\sum}_{k=1}^{n}{\alpha}_{k} represents at least 95% of the total variance of the process, {\sum}_{k=1}^{\mathrm{\infty}}{\alpha}_{k}=2{\int}_{T}{r}_{x}\left(t,t\right)F\left(t\right)\mathsf{\text{d}}t (see the proof of Lemma 1 in the "Appendix").

5)
Finally, from a discrete set of observations, x_{1}, ..., x_{ N }, we can compute the integrals in (7) by means of
\begin{array}{c}\underset{T}{\int}{h}_{1}\left(t,\tau \right)x\left(\tau \right)F\left(\tau \right)\mathsf{\text{d}}\tau \approx \sum _{k=1}^{n}{g}_{1}\left(t,k\right){x}_{k}\\ \underset{T}{\int}{h}_{2}\left(t,\tau \right){x}^{*}\left(\tau \right)F\left(\tau \right)\mathsf{\text{d}}\tau \approx \sum _{k=1}^{n}{g}_{2}\left(t,k\right){x}_{k}^{*}\end{array}
where the weights g_{1}(t, k) and g_{2}(t, k) are obtained via a suitable method that performs numerical integration with integrands constituted for discrete points. For example, using the GillMiller quadrature method [36] implemented by subroutine d01gaf from the NAG Toolbox for MATLAB or the trapezoidal rule (trapz function in MATLAB).
The only changes for implementing the estimator (2) are in steps 1 and 3, where we have to use r_{ x }(t, τ) and their associated eigenvalues and eigenfunctions, {λ_{ k }} and {ϕ_{ k }(t)}, instead.
4 Numerical Examples
Three examples illustrate the implementation of the proposed solution and show its capability to solve very general estimation problems. Example 1 shows a situation where true eigenvalues and eigenfunctions are available and aims at comparing the performance of WL processing in relation to SL processing. Example 2 applies the RR method to approximate the eigenexpansion and also illustrates its implementation with discrete data. Finally, Example 3 considers an application in seismic signal processing in which the groundmotion velocity is estimated from seismic ground acceleration data.
4.1 Example 1
Assume that a real waveform s(t) is transmitted over a channel that rotates it by some random phase θ and adds a noise n(t). Unlike [28] and [29], we consider infinite observation intervals and a multiplicative quadratic noise in the observations. More precisely, s(t) is defined on the real line, S = ℝ, with zeromean and {r}_{s}\left(t,\tau \right)={\mathsf{\text{e}}}^{{\left(t\tau \right)}^{2}}. Thus, the observation process is given by
where \mathsf{\text{j}}=\sqrt{1} and the noise n(t) is a zeromean Gaussian process with r_{ n }(t, τ) = 3^{1/2}p^{1/4}(t)p^{1/4}(τ), where p\left(t\right)=\sqrt{2/\pi}{\mathsf{\text{e}}}^{2{t}^{2}} (this type of process is studied in [34]). Three different probabilistic distributions for θ are taken: a uniform distribution on (σ, σ), a zeromean normal with variance σ, and a Laplace distribution with zeromean and variance σ. Several choices of σ will be used to show how the advantages of WL processing vary with the level of improperness of the observations. Finally, mutual independence of θ, s(t) and n(t) is assumed. The objective is to estimate \u1e61\left(t\right),t\in \left[0,1\right], where \u1e61\left(t\right) denotes the MS derivative of s(t).
We first notice that {\int}_{\mathrm{\infty}}^{\mathrm{\infty}}{r}_{x}\left(t,t\right)\mathsf{\text{d}}t<\mathrm{\infty}, where F(t) = 1 has been selected by a trialanderror method and thus, condition (1) is verified. This example is one of the particular cases where calculation of true eigenvalues and eigenfunctions is possible. In fact, r_{ x }(t, τ) has eigenvalues (1+E\left[{\mathsf{\text{e}}}^{\mathsf{\text{2j}}\theta}\right]{\stackrel{\u0304}{\lambda}}_{k} and \left(1E\left[{\mathsf{\text{e}}}^{\mathsf{\text{2j}}\theta}\right]\right){\stackrel{\u0304}{\lambda}}_{k} with respective associated eigenfunctions {[{\varphi}_{k}\left(t\right)/\sqrt{2},{\varphi}_{k}\left(t\right)/\sqrt{2}]}^{\prime} and {[\mathsf{\text{j}}{\varphi}_{k}\left(t\right)/\sqrt{2},\mathsf{\text{j}}{\varphi}_{k}\left(t\right)/\sqrt{2}]}^{\prime}, k = 0, ..., and where {\stackrel{\u0304}{\lambda}}_{k}=\sqrt{\frac{2}{2+\sqrt{3}}}{\left(\frac{1}{2+\sqrt{3}}\right)}^{k}, {\varphi}_{k}\left(t\right)={2}^{k}k!\frac{1}{3}{3}^{3/4}{\mathsf{\text{e}}}^{\left(\sqrt{3}1\right){t}^{2}}{H}_{k}\left(\sqrt{2\sqrt{3}}t\right) and {H}_{k}\left(t\right)={\left(1\right)}^{k}{\mathsf{\text{e}}}^{{t}^{2}}\frac{{\partial}^{k}}{\partial {t}^{k}}{\mathsf{\text{e}}}^{{t}^{2}} are the Hermite polynomials. Moreover, we can check that the associated MS errors are the following:
with {l}_{k}\left(t\right)={3}^{1/2}{\int}_{T}\frac{\partial}{\partial t}{r}_{s}\left(t,\tau \right){p}^{1/2}\left(\tau \right){\varphi}_{k}\left(\tau \right)\mathsf{\text{d}}\tau.
We use the measure
which is closely related to the performance measure considered in [29], to compare the performance of WL processing in relation to SL processing. For that, we have truncated the series in P_{SL}(t) and P_{WL}(t) at n = 10 terms (this approximate expansion explains 99.86% of the total variance of the process). The performance of both the SL and the WL estimators for n = 10 does not really vary substantially from the case of n > 10. Figure 1a depicts the measure I in function of σ for the three probabilistic distributions considered for θ. It turns out that the advantages of WL processing decrease in both cases as σ tends toward zero and as σ tends toward infinity. However, this occurs for different reasons. Another performance measure which helps in the interpretation is
which, for this example, takes the value L = E[e^{2jθ}]. Figure 1b shows the index L as a function of σ for the three probabilistic distributions considered for θ. On the one hand, as σ tends toward zero, then the index L tends to one since in that limit the observation process becomes a real signal^{4}. On the other hand, when σ increases, then L tends toward zero since x(t) becomes a proper signal. The faster convergence to zero in the normal case and the slower one for the Laplace distribution are also observed.
4.2 Example 2
We study a generalization of the classical communication example addressed in [28] and [29]. Assume that a real waveform s_{1}(t) is transmitted over a channel that rotates it by a standard normal phase θ_{1} and adds a nonwhite noise n(t). More precisely, s_{1}(t) is defined on the interval [0, 1], with zeromean and {r}_{{s}_{1}}\left(t,\tau \right)=min\left\{t,\tau \right\}. Thus, the observation process is
where the nonwhite noise n(t) is obtained from a linear timeinvariant system of the form n\left(t\right)={\mathsf{\text{e}}}^{\mathsf{\text{j}}{\theta}_{\mathsf{\text{2}}}}\underset{0}{\overset{1}{\int}}{r}_{{s}_{1}}\left(t,\tau \right){s}_{2}\left(\tau \right)\mathsf{\text{d}}\tau, with θ_{2} being a zeromean normal random variable with variance 2 and s_{2}(t) a standard Wiener process (these types of noises appear in [[37], p. 357]). Moreover, we assume that θ_{1}, θ_{2}, s_{1}(t), and s_{2}(t) are independent of each other. This example extends the cases studied in [28] and [29] since the considered noise here does not have a white component and thus, the previous solutions cannot be applied. The observations have been taken in the following time instants: i/ 1000, i = 1, ..., 1000. The objective is to estimate s\left(t\right)={\mathsf{\text{e}}}^{\mathsf{\text{j}}{\theta}_{\mathsf{\text{1}}}}{s}_{1}\left(t\right), t ∈ [0,1].
We first notice that {\int}_{0}^{1}{r}_{x}\left(t,t\right)\mathsf{\text{d}}t<\mathrm{\infty}, where F(t) = 1 has been selected since the processes involved are continuous and thus, condition (1) is verified. Now, to apply the RR method, we choose the Fourier basis of complex exponentials on [0, 1], {\left\{exp\left\{2\pi \mathsf{\text{j}}k\right\}\right\}}_{k=\mathrm{\infty}}^{\mathrm{\infty}}. Following the recommendations in step 5 of Section 3.1, we compute the integrals in (7) via the subroutines d01gaf and trapz (there were no significative differences between both methods).
Figure 2 depicts the MS error P_{WL}(t) together with the MS errors of the WL estimator obtained from the RR method with n = 25 and n = 50 terms in step 5 of the algorithm, which have been generated by Monte Carlo simulation (a total of 10,000 simulations were performed). We can see that the method may yield a sufficiently accurate solution with a short number n of terms while reducing the complexity of the problem significantly. Note that a truncated expansion at n = 25 terms explains 88.77% of the total variance of the process and the expansion with n = 50 terms 95.81%.
4.3 Example 3
The seismic ground acceleration can be represented by a uniformly modulated nonstationary process [33]. The modulated nonstationary process is obtained in the following way
where a(t) is a time modulating function that could be a complex function, and z(t) is a stationary process with zeromean and known secondorder moments. In general, the socalled exponential modulating function is adopted [38, 39]. A common choice for z(t) is the standard OrnsteinUhlenbeck process with a particular version of the exponential modulating function given by a(t) = e^{t} [[33], p. 38]. Thus, the seismic ground acceleration can be modeled as a stochastic signal {s(t), t ∈ S = ℝ^{+}} with r_{ s }(t, τ) = e^{(t+τ)}e^{tτ}. Consider the observation process
where θ is a standard normal phase independent of s(t). Now, the objective is to estimate the seismic ground velocity at instant t ≥ 2, i.e., \xi \left(t\right)={\int}_{0}^{1}s\left(\tau \right)\mathsf{\text{d}}\tau, with t ∈ S' = [2, ∞). A justification for considering infinite intervals on the basis of the stationarity property of z(t) can be found in [40].
By using a trialanderror method, we select F(t) = e^{t}and then, (1) holds. For the case of infinite intervals, T = ℝ^{+}, the true eigenvalues and eigenfunctions of r_{ x }(t, τ) are not known. We approximate them by means of the RR method. The RR eigenvalues and eigenfunctions of r_{ x }(t, τ) are \left(1\phantom{\rule{2.77695pt}{0ex}}\pm \phantom{\rule{2.77695pt}{0ex}}{\mathsf{\text{e}}}^{2}\right){\stackrel{\u0304}{\lambda}}_{k} and {\left[{\stackrel{\u0303}{\varphi}}_{k}\left(t\right)/\sqrt{2},{\stackrel{\u0303}{\varphi}}_{k}\left(t\right)/\sqrt{2}\right]}^{\prime} and {\left[\mathsf{\text{j}}{\stackrel{\u0303}{\varphi}}_{k}\left(t\right)/\sqrt{2},\mathsf{\text{j}}{\stackrel{\u0303}{\varphi}}_{k}\left(t\right)/\sqrt{2}\right]}^{\prime}, where {\stackrel{\u0303}{\lambda}}_{k} and {\stackrel{\u0303}{\varphi}}_{k}\left(t\right) are the RR eigenvalues and eigenfunctions, respectively, of r_{ x }(t, τ) obtained from the following trigonometric basis
In Figure 3, we compare the MS error of the SL estimator calculated with n = 10 terms with the MS errors of the WL estimator with n = 2, 4 and, 10 terms (which account for 57.60, 82.30 and 93.88% of the total variance of x(t), respectively). We have limited the estimation interval to [2, 6] because of the observed stabilization of the MS errors for t ≥ 4. Apart from the better performance of the WL estimator with respect to the SL estimator (as was to be expected), the rapid convergence of the RR estimators is also confirmed.
5 Concluding Remarks
A new WL estimator has been given for solving general continuoustime estimation problems. The formulation considered can be adapted in order to include as particular cases a great number of estimation problems of interest. The proposed estimator becomes a way that avoids explicit calculation of matrix inverses altogether and can be applied provided that the secondorder characteristics of the processes involved are known. Such knowledge is usual in some practical problems in fields as diverse as seismic signal processing, signal detection, finite element analysis, etc. An alternative procedure is the stochastic gradientbased iterative solution called augmented complex least meansquare algorithm (see, e.g., [24]) in which the secondorder statistics are estimated from data. However, if we wish to take advantage of the knowledge of the secondorder characteristics and the number of observation data is very large, then the continuoustime solution is a recommended option.
Appendix
This "Appendix" is written following a rigorous mathematical formalism parallel to [15] or [30]. Condition (1) is indeed more restrictive than the one imposed in the works of Cambanis. Specifically, suppose μ a measure on \left(T,\mathcal{B}\left(T\right)\right) (\mathcal{B}\left(T\right) is the σalgebra of Lebesgue measurable subsets of T) which is equivalent to the Lebesgue measure and verifies
The existence of μ satisfying (9) is proved in [30]. Cambanis also shows that (9) allows us to select a function F(t) such that dμ(t)/ dt = F(t) and (1) holds.
Theorem 1 If x(t) is proper, then
with {\stackrel{\u0304}{b}}_{k}\left(t\right)=\frac{1}{{\lambda}_{k}}{\int}_{T}{\rho}_{2}\left(t,\tau \right){\varphi}_{k}^{*}\left(\tau \right)\mathsf{\text{d}}\mu \left(\tau \right). Moreover, its associated MS error is
Proof: Firstly, notice that if x(t) is proper, then the members of the set of random variables \left\{{\epsilon}_{k}\right\}\cup \left\{{\epsilon}_{k}^{*}\right\} are orthogonal. Thus, the estimator {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right) is obtained by projecting the functional ξ(t) onto the Hilbert space generated by {ε_{ k }} and \left\{{\epsilon}_{k}^{*}\right\}, H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right). Hence, the estimator can be expressed in the form {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)={\sum}_{k=1}^{\mathrm{\infty}}{b}_{k}\left(t\right){\epsilon}_{k}+{\sum}_{k=1}^{\mathrm{\infty}}{\stackrel{\u0304}{b}}_{k}\left(t\right){\epsilon}_{k}^{*}, where the coefficients b_{ k }(t) and {\stackrel{\u0304}{b}}_{k}\left(t\right) are determined via the projection theorem of the Hilbert spaces. This result assures that \xi \left(t\right){\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)\perp \left\{{\epsilon}_{k}\right\}\cup \left\{{\epsilon}_{k}^{*}\right\}; that is, E\left[\xi \left(t\right){\epsilon}_{k}^{*}\right]=E\left[{\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right){\epsilon}_{k}^{*}\right] and E\left[\xi \left(t\right){\epsilon}_{k}\right]=E\left[{\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right){\epsilon}_{k}\right], for all k. Since E\left[\xi \left(t\right){\epsilon}_{k}^{*}\right]={\int}_{T}{\rho}_{1}\left(t,\tau \right){\varphi}_{k}\left(\tau \right)\mathsf{\text{d}}\mu \left(\tau \right), E\left[{\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right){\epsilon}_{k}^{*}\right]={\lambda}_{k}{b}_{k}\left(t\right), E\left[\xi \left(t\right){\epsilon}_{k}\right]={\int}_{T}{\rho}_{2}\left(t,\tau \right){\varphi}_{k}^{*}\left(\tau \right)\mathsf{\text{d}}\mu \left(\tau \right), and E\left[{\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right){\epsilon}_{k}\right]={\lambda}_{k}{\stackrel{\u0304}{b}}_{k}\left(t\right), then the first part of the result follows.
On the other hand, the corresponding MS error is
■
We need the following Lemma before proving Theorem 2.
Lemma 1
Proof: From (9), we get that r_{ x }(t, τ) is the kernel of an integral operator of L_{2}(μ × μ) into L_{2}(μ × μ), which is linear, selfadjoint, nonnegativedefinite, and compact. Let {α_{ k }} be their eigenvalues and {φ_{ k }(t)} the corresponding eigenfunctions. The eigenfunctions {\phi}_{k}\left(t\right)={\left[{f}_{k}\left(t\right),{f}_{k}^{*}\left(t\right)\right]}^{\prime} are orthonormal in the following sense
Thus, the real random variables given by (4) are trivially orthogonal, i.e., E[w_{ n }w_{ m }] = a_{ n }δ_{ nm }.
First, we prove that H\left({w}_{k}\right)\subseteq H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right). Let H\left({\epsilon}_{k}^{*}\right) be the Hilbert space spanned by the random variables \left\{{\epsilon}_{k}^{*}\right\}. From Theorem 6 of [30], we have \underset{T}{\int}x\left(t\right){f}_{k}^{*}\left(t\right)\mathsf{\text{d}}\mu \left(t\right)\phantom{\rule{1em}{0ex}}\mathsf{\text{a}}\mathsf{\text{.s}}\mathsf{\text{.}}\in H\left({\epsilon}_{k}\right) and \underset{T}{\int}{x}^{*}\left(t\right){f}_{k}\left(t\right)\mathsf{\text{d}}\mu \left(t\right)\phantom{\rule{1em}{0ex}}\mathsf{\text{a}}\mathsf{\text{.s}}\mathsf{\text{.}}\in H\left({\epsilon}_{k}^{*}\right) and hence it is trivial that {w}_{k}\subseteq H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right).
Now, we demonstrate that H\left({\epsilon}_{k},{\epsilon}_{k}^{*}\right)\subseteq H\left({w}_{k}\right). For that, we begin to check that ε_{ k } ∈ H(w_{ k }). By projecting x(t) onto H(w_{ k }), we obtain that x(t) = y(t) + v(t) with y\left(t\right)={\sum}_{k=1}^{\mathrm{\infty}}{f}_{k}\left(t\right){w}_{k} and y(t) is perpendicular to v(t). Thus, we have that r_{ x }(t, τ) = r_{ y }(t, τ) + r_{ v }(t, τ) where r_{ y }(t, τ) = E[y(t)y*(τ)] and r_{ v }(t, τ) = E[v(t)v*(τ)]. By the monotone convergence theorem and (10), we get that {\int}_{T}{r}_{x}\left(t,t\right)\mathsf{\text{d}}\mu \left(t\right)=\frac{1}{2}{\sum}_{k=1}^{\mathrm{\infty}}{\alpha}_{k}+{\int}_{T}{r}_{v}\left(t,t\right)\mathsf{\text{d}}\mu \left(t\right).
On the other hand, {\int}_{T}{r}_{x}\left(t,t\right)\mathsf{\text{d}}\mu \left(t\right)=\frac{1}{2}\mathsf{\text{Tr}}({r}_{x}\mathsf{\text{)}}=\frac{1}{2}{\sum}_{k=1}^{\mathrm{\infty}}{\alpha}_{k}, where Tr(r_{ x }) is the trace of the integral operator on L_{2}(μ × μ) with kernel r_{ x }(t, τ).
Thus,
and hence
Now, we consider the integral {\eta}_{k}={\int}_{T}y\left(t\right){\varphi}_{k}^{*}\left(t\right)\mathsf{\text{d}}\mu \mathsf{\text{(}}t\mathsf{\text{)}} a.s. From (12), we have
and then η_{ k } ∈ H(w_{ k }). Moreover, it follows that E[ε_{ k }  η_{ k }^{2}] = 0 and then ε_{ k } = η_{ k } ∈ H(w_{ k }).
Similarly, it can be proved that {\epsilon}_{k}^{*}\in H\left({w}_{k}\right). ■
Theorem 2 If x(t) is improper, then
where {\psi}_{k}\left(t\right)=\frac{1}{{\alpha}_{k}}\left({\int}_{T}{\rho}_{1}\left(t,\tau \right){f}_{k}\left(\tau \right)\mathsf{\text{d}}\mu \left(\tau \right)+{\int}_{T}{\rho}_{2}\left(t,\tau \right){f}_{k}^{*}\left(\tau \right)\mathsf{\text{d}}\mu \left(\tau \right)\right). Moreover, its corresponding MS error is
Proof: Following a reasoning similar to that of proof of Theorem 1 and taking Lemma 1 into account, the result is immediate. ■
In the next result, we provide conditions in order to hold (7).
Theorem 3 The WL estimator can be expressed in the following closed form
for some h_{1}(t, ·), h_{2}(t, ·) ∈ L_{2}(μ) if and only if for some h_{1}(t, ·), h_{2}(t, ·) ∈ L_{2}(μ) it is satisfied that
for t ∈ S', a.e. τ ~ [Leb].
Proof: From (11), we have
Suppose that {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right) satisfies (13). It follows from \xi \left(t\right){\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)\perp H\left({w}_{k}\right) and (15) that E\left[\xi \left(t\right){x}^{*}\left(\tau \right)\right]=E\left[{\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right){x}^{*}\left(\tau \right)\right] and E\left[\xi \left(t\right)x\left(\tau \right)\right]=E\left[{\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)x\left(\tau \right)\right], for almost all τ ∈ T [Leb], and thus we obtain (14).
Reciprocally, suppose that (14) holds. Define the process
Theorem 6 of [30] guarantees that η(t) ∈ H(w_{ k }). Moreover, from (14), we obtain that ξ(t)  η(t)⊥x(τ) and ξ(t)  η(t)⊥x*(t) for almost all τ ∈ T [Leb]. Hence, from the projection theorem of the Hilbert spaces {\widehat{\xi}}_{\mathsf{\text{WL}}}\left(t\right)=\eta \left(t\right) a.s. ■
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Acknowledgements
This work was supported in part by Project MTM200766791 of the Plan Nacional de I+D+I, Ministerio de Educación y Ciencia, Spain. This project is financed jointly by the FEDER.
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MartínezRodríguez, A.M., NavarroMoreno, J., FernándezAlcalá, R.M. et al. A general solution to the continuoustime estimation problem under widely linear processing. EURASIP J. Adv. Signal Process. 2011, 119 (2011). https://doi.org/10.1186/168761802011119
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DOI: https://doi.org/10.1186/168761802011119